May 2004 doc.: IEEE 802.11-03/940r4
Submission page 1 Vinko Erceg, Zyray Wireless; et al.
IEEE P802.11
Wireless LANs
TGn Channel Models
Date: May 10, 2004
Authors:
Vinko Erceg
Zyray Wireless; e-Mail: verceg@zyraywireless.com
Laurent Schumacher
Namur University; e-Mail: laurent.schumacher@ieee.org
Persefoni Kyritsi
Stanford University; e-Mail: kyritsi@math.stanford.edu
Andreas Molisch, Mitsubishi Electric
Daniel S. Baum, ETH University
Alexei Y. Gorokhov, Philips Research
Claude Oestges, Louvain University
Qinghua Li, Intel
Kai Yu, KTH
Nir Tal, Metalink
Bas Dijkstra, Namur University
Adityakiran Jagannatham, U.C. San Diego
Colin Lanzl, Aware
Valentine J. Rhodes, Intel
Jonas Medbo, Ericsson
Dave Michelson, UBC
Mark Webster, Intersil
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WLAN
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Eric Jacobsen, Intel
David Cheung, Intel
Clifford Prettie, Intel
Minnie Ho, Intel
Steve Howard, Qualcomm
Bjorn Bjerke, Qualcomm
Lung Jengx, Intel
Hemanth Sampath, Marvell
Severine Catreux, Zyray Wireless
Stefano Valle, ST Microelectronics
Angelo Poloni, ST Microelectronics
Antonio Forenza, University of Texas at Austin
Robert W. Heath, University of Texas at Austin
Abstract
This document provides the channel models to be used for the High Throughput Task Group
(TGn).
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List of Participants
Vinko Erceg (Zyray Wireless)
Laurent Schumacher (Namur University)
Persefoni Kyritsi (Aalborg University)
Daniel Baum (ETH University)
Andreas Molisch (Mitsubishi Electric)
Alexei Gorokhov (Philips Research)
Valentine J. Rhodes (Intel)
Srinath Hosur (Texas Instruments)
Srikanth Gummadi (Texas Instruments)
Eilts Henry (Texas Instruments)
Eric Jacobsen (Intel)
Sumeet Sandhu (Intel)
David Cheung (Intel)
Qinghua Li (Intel)
Clifford Prettie (Intel)
Heejung Yu (ETRI)
Yeong-Chang Maa (InProComm)
Richard van Nee (Airgo)
Jonas Medbo (Ericsson)
Eldad Perahia (Cisco Systems)
Brett Douglas (Cisco Systems)
Helmut Boelcskei (ETH Univ.)
Yong Je Lim (Samsung)
Massimiliano Siti (ST)
Stefano Valle (ST)
Steve Howard (Qualcomm)
Bjorn Bjerke (Qualcomm)
Qinfang Sun (Atheros)
Won-Joon Choi (Atheros)
Ardavan Tehrani (Atheros)
Jeff Gilbert (Atheros)
Hemanth Sampath (Marvell)
H. Lou (Marvell)
Ravi Narasimhan (Marvell)
Pieter van Rooyen (Zyray Wireless)
Pieter Roux (Zyray Wireless)
Majid Malek (HP)
Timothy Wakeley (HP)
Dongjun Lee (Samsung)
Tomer Bentzion (Metalink)
Nir Tal (Metalink)
Amir Leshem (Metalink, Bar IIan University)
Guy Shochet (Metalink)
Patric Kelly (Bandspeed)
Vafa Ghazi (Cadence)
Mehul Mehta (Synad Technologies)
Bobby Jose (Mabuhay Networks)
Charles Farlow (California Amplifier)
Claude Oestges (Louvain University)
Robert W. Heath (Univ. of Texas at Austin)
Dave Michelson (UBC)
Mark Webster (Intersil)
Dov Andelman (Envara)
Colin Lanzl (Aware)
Kai Yu (KTH)
Irina Medvedev (Qualcomm)
John Ketchum (Qualcomm)
Adrian Stephens (Intel)
Jack Winters (Motia)
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Revision History
Date Version Description of changes
1/9/04 01 Paragraph added in Sec. 4.1 describing K-factor simulation procedure.
Paragraph added in Sec. 4.5.1 describing high AP antenna placements.
3/5/04 02 Correction of autocorrelation function and coherence time formula in
Sec 4.7.1 (inclusion of fd). Equations (4) and (7) were updated.
5/4/04 03 Table IIb removed to provide consistency with updated UM
(03/802r17); added table of mean and standard deviation of cluster rms
delay spread in section 4.5.1; renumbered figures to be consistent.
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AoA/AoD=45° removed
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section 4.1 (Figure 2),
renumbered figures (including
figures in appendices) and altered
references to how clusters
constructed to emphasize that they
are NLOS;
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1. Introduction
Multiple antenna technologies are being considered as a viable solution for the next
generation of mobile and wireless local area networks (WLAN). The use of multiple antennas
offers extended range, improved reliability and higher throughputs than conventional single
antenna communication systems. Multiple antenna systems can be generally separated into
two main groups: smart antenna based systems and spatial multiplexing based multiple-input
multiple-output (MIMO) systems.
Smart antenna based systems exploit multiple transmit and/or receive antennas to provide
diversity gain in a fading environment, antenna gain and interference suppression. These
gains translate into improvement of the spectral efficiency, range and reliability of wireless
networks. These systems may have an array of multiple antennas only at one end of the
communication link (e.g., at the transmit side, such as multiple-input single-output (MISO)
systems; or at the receive side, such as single-input multiple-output (SIMO) systems; or at
both ends (MIMO) systems). In MIMO systems, each transmit antenna can broadcast at the
same time and in the same bandwidth an independent signal sub-stream. This corresponds to
the second category of multi-antennas systems, referred to as spatial multiplexing-based
multiple-input multiple-output (MIMO) systems. Using this technology with n transmit and n
receive antennas, for example, an n-fold increase in data rate can be achieved over a single
antenna system [1]. This breakthrough technology appears promising in fulfilling the growing
demand for future high data rate PAN, WLAN, WAN, and 4G systems.
In this document we propose a set of channel models applicable to indoor MIMO WLAN
systems. Some of the channel models are an extension of the single-input single-output (SISO)
WLAN channel models proposed by Medbo et al. [2,3]. The newly developed multiple
antenna models are based on the cluster model developed by Saleh and Valenzuela [4], and
further elaborated upon by Spencer et al. [5], Cramer et al. [6], and Poon and Ho [7]. Indoor
SISO and MIMO wireless channels were further analyzed in [8-18].
A step-wise development of the new models follows: In each of the three models (A-C) in [2]
and three additional models distinct clusters were identified first. The number of clusters
varies from 2 to 6, depending on the model. This finding is consistent with numerous
experimentally determined results reported in the literature [4-7,9,10] and also using ray-
tracing methods [8]. The power of each tap in a particular cluster was determined so that the
sum of the powers of overlapping taps corresponding to different clusters corresponds to the
powers of the original power delay profiles. Next, angular spread (AS), angle-of-arrival
(AoA), and angle of departure (AoD) values were assigned to each tap and cluster (using
statistical methods) that agree with experimentally determined values reported in the
literature. Cluster AS was experimentally found to be in the 20o to 40o range [5-10], and the
mean AoA was found to be random with a uniform distribution. With the knowledge of each
tap power, AS, and AoA (AoD), for a given antenna configuration, the channel matrix H can
be determined. The channel matrix H fully describes the propagation channel between all
transmit and receive antennas. If the number of receive antennas is n and transmit antennas is
m, the channel matrix H has a dimension of n x m. To arrive at channel matrix H, we use a
method that employs correlation matrix and i.i.d. matrix (zero-mean unit variance
independent complex Gaussian random variables). The correlation matrix for each tap is
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的: 突出显示
带格式的: 突出显示
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Submission page 6 Vinko Erceg, Zyray Wireless; et al.
based on the power angular spectrum (PAS) with AS being the second moment of PAS
[19,20]. To verify the newly developed model, we have calculated the channel capacity
assuming the narrowband case and compared it to experimentally determined capacity results
with good agreement.
The model can be used for both 2 GHz and 5 GHz frequency bands, since the experimental
data and published results for both bands were used in developing the model (average, rather
than frequency dependent model). However, path loss model is frequency dependent.
The paper is organized as follows. In Sec. 2 we describe SISO WLAN models. Section 3
formulates the MIMO channel matrix. Section 4 describes the clustering approach and the
method for model parameters calculation. In Sec. 5 we summarize the model parameters. In
Sec. 6 we briefly describe the Matlab program. Section 7 presents the antenna correlation and
channel capacity results using the models, and with Sec. 8 we conclude.
2. SISO WLAN Models
A set of WLAN channel models was developed by Medbo et al. [2,3]. In [2], five delay
profile models were proposed for different environments (Models A-E):
• Model A for a typical office environment, non-line-of-sight (NLOS) conditions, and
50 ns rms delay spread.
• Model B for a typical large open space and office environments, NLOS conditions,
and 100 ns rms delay spread.
• Model C for a large open space (indoor and outdoor), NLOS conditions, and 150 ns
rms delay spread.
• Model D, same as model C, line-of-sight (LOS) conditions, and 140 ns rms delay
spread (10 dB Ricean K-factor at the first delay).
• Model E for a typical large open space (indoor and outdoor), NLOS conditions, and
250 ns rms delay spread.
We use models A-C together with three additional models more representative of smaller
environments, such as residential homes and small offices, for our modeling purposes. The
resulting models that we propose are as follows:
• Model A (optional, should not be used for system performance comparisons), flat
fading model with 0 ns rms delay spread (one tap at 0 ns delay model). This model
can be used for stressing system performance, occurs small percentage of time
(locations).
• Model B with 15 ns rms delay spread.
• Model C with 30 ns rms delay spread.
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• Model D with 50 ns rms delay spread.
• Model E with 100 ns rms delay spread.
• Model F with 150 ns rms delay spread.
Model mapping to a particular environment is presented in table IIb.
The tables with channel coefficients (tap delays and corresponding powers) can be found in
Appendix C.
The path loss model that we propose consists of the free space loss LFS (slope of 2) up to a
breakpoint distance and slope of 3.5 after the breakpoint distance [21]. For each of the
models different break-point distance dBP was chosen
L(d) = LFS(d) d <= dBP
L(d) = LFS(dBP) + 35 log10(d / dBP) d > dBP (1)
where d is the transmit-receive separation distance in m. The path loss model parameters are
summarized in Table I. In the table, the standard deviations of log-normal (Gaussian in dB)
shadow fading are also included. The values were found to be in the 3-14 dB range [16].
New Model dBP (m) Slope before
dBP
Slope after
dBP
Shadow
fading std.
dev. (dB)
before dBP
(LOS)
Shadow
fading std.
dev. (dB)
after dBP
(NLOS)
A (optional) 5 2 3.5 3 4
B 5 2 3.5 3 4
C 5 2 3.5 3 5
D 10 2 3.5 3 5
E 20 2 3.5 3 6
F 30 2 3.5 3 6
Table I: Path loss model parameters
The zero-mean Gaussian probability distribution is given by
⎟⎟⎠
⎞
⎜⎜⎝
⎛−
= 2
2
2exp
2
1)( σσπ
x
xp (2)
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Submission page 8 Vinko Erceg, Zyray Wireless; et al.
3. MIMO Matrix Formulation
We follow the MIMO modeling approach presented in [11,20] that utilizes receive and
transmit correlation matrices. The MIMO channel matrix H for each tap, at one instance of
time, in the A-F delay profile models can be separated into a fixed (constant, LOS) matrix
and a Rayleigh (variable, NLOS) matrix [22] (4 transmit and 4 receive antennas example)
⎟⎟
⎟⎟
⎟
⎠
⎞
⎜⎜
⎜⎜
⎜
⎝
⎛
⎥⎥
⎥⎥
⎦
⎤
⎢⎢
⎢⎢
⎣
⎡
++
⎥⎥
⎥⎥
⎥
⎦
⎤
⎢⎢
⎢⎢
⎢
⎣
⎡
+=
⎟⎟⎠
⎞
⎜⎜⎝
⎛
+++=
44434241
34333231
24232221
14131211
1
1
1
1
1
1
44434241
34333231
24232221
14131211
XXXX
XXXX
XXXX
XXXX
K
eeee
eeee
eeee
eeee
K
KP
H
K
H
K
KPH
jjjj
jjjj
jjjj
jjjj
vF
φφφφ
φφφφ
φφφφ
φφφφ
(3)
where Xij (i-th receiving and j-th transmitting antenna) are correlated zero-mean, unit
variance, complex Gaussian random variables as coefficients of the variable NLOS (Rayleigh)
matrix HV, exp(jφij) are the elements of the fixed LOS matrix HF, K is the Ricean K-factor,
and P is the power of each tap. We assume that each tap consists of a number of individual
rays so that the complex Gaussian assumption is valid. P in (3) represents the sum of the
fixed LOS power and the variable NLOS power (sum of powers of all taps).
To correlate the Xij elements of the matrix X, the following method can be used
[ ] [ ] [ ] [ ]( )1/ 2 1/ 2 Trx iid txX R H R= (4)
where Rtx and Rrx are the receive and transmit correlation matrices, respectively, and Hiid is a
matrix of independent zero mean, unit variance, complex Gaussian random variables, and
[ ] [ ]
[ ] [ ]rxijrxR
txijtxR
ρ
ρ
=
= (5)
where ρtxij are the complex correlation coefficients between i-th and j-th transmitting
antennas, and ρrxij are the complex correlation coefficients between i-th and j-th receiving
antennas. An alternative approach uses the Kronecker product of the transmit and receive
correlation matrices (Hiid is an array in this case instead of matrix)
[ ] [ ] [ ]{ } [ ]1 / 2X R R Htx rx iid= ⊗ (6)
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Following is an example of 4 x 4 MIMO channel transmit and receive correlation matrices
12 13 14
21 23 24
31 32 34
41 42 43
1
1
1
1
tx tx tx
tx tx tx
tx
tx tx tx
tx tx tx
R
ρ ρ ρ
ρ ρ ρ
ρ ρ ρ
ρ ρ ρ
⎡ ⎤⎢ ⎥⎢ ⎥⎢ ⎥= ⎢ ⎥⎢ ⎥⎢ ⎥⎣ ⎦
(7)
12 13 14
21 23 24
31 32 34
41 42 43
1
1
1
1
rx rx rx
rx rx rx
rx
rx rx rx
rx rx rx
R
ρ ρ ρ
ρ ρ ρ
ρ ρ ρ
ρ ρ ρ
⎡ ⎤⎢ ⎥⎢ ⎥⎢ ⎥= ⎢ ⎥⎢ ⎥⎢ ⎥⎣ ⎦
The complex correlation coefficient values calculation for each tap is based on the power
angular spectrum (PAS) with angular spread (AS) being the second moment of PAS [19,20].
Using the PAS shape, AS, mean angle-of-arrival (AoA), and individual tap powers,
correlation matrices of each tap can be determined as described in [20]. For the uniform
linear array (ULA) the complex correlation coefficient at the linear antenna array is expressed
as
)()( DjRDR XYXX +=ρ (8)
where λπ /2 dD = , and RXX and RXY are the cross-correlation functions between the real parts
(equal to the cross-correlation function between the imaginary parts) and between the real
part and imaginary part, respectively, with
∫
−
=
π
π
φφφ dPASDDXXR )()sincos()( (9)
and
∫
−
=
π
π
φφφ dPASDDXYR )()sinsin()( (10)
Expressions for correlation coefficients assuming uniform, truncated Gaussian, and truncated
Laplacian PAS shapes can be found in [20]. To calculate the numerical values of correlation
matrices we use a Matlab program developed and distributed by L. Schumacher [23] (see Sec.
6).
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⎢⎢
⎢⎢
⎢⎢
⎣
⎡
=
41
31
21
1
tx
tx
tx
txR
ρ
ρ
ρ
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⎢⎢
⎢⎢
⎢⎢
⎣
⎡
=
41
31
21
1
rx
rx
rx
rxR
ρ
ρ
ρ
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Next we briefly describe the various steps in our cluster modeling approach. We
• Start with delay profiles of models B-F.
• Manually identify clusters in each of the five models.
• Extend clusters so that they overlap, determine tap powers (see Appendix A).
• Assume PAS shape of each cluster and corresponding taps (Laplacian).
• Assign AS to each cluster and corresponding taps.
• Assign mean AoA (AoD) to each cluster and corresponding taps.
• Assume antenna configuration.
• Calculate correlation matrices for each tap.
In the next section we elaborate on the above steps.
4. Cluster Modeling Approach
The cluster model was introduced first by Saleh and Valenzuela [4] and later verified,
extended, and elaborated upon by many other researchers in [5-10]. The received signal
amplitude βkl is a Rayleigh-distributed random variable with a mean-square value that obeys
a double exponential decay law
γτββ //22 )0,0( kll ee Tkl −Γ−= (11)
where )0,0(2β represents the average power of the first arrival of the first cluster, Tl
represents the arrival time of the lth cluster, and τkl is the arrival time of the kth arrival within
the lth cluster, relative to Tl. The parameters Γ and γ determine the inter-cluster signal level
rate of decay and the intra-cluster rate of decay, respectively. The rates of the cluster and ray
arrivals can be determined using exponential rate laws
)(1 1)|( −
−Λ−
− Λ= ll TTll eTTp (12)
)(,1 1)|( −
−−
− = ll TTlkkl ep λλττ (13)
where Λ is the cluster arrival rate and λ is the ray arrival rate.
For our modeling purposes we are not using the equations (11) through (13) since the delay
profile characteristics are already predetermined by the model B-F delay profiles.
4.1 Number of clusters
The number of clusters found in different indoor environments varies between 1 and 7. In [5],
the average number of clusters was found to be 3 for one building, and 7 for another building.
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In [7] the number of clusters reported was found to be 2 for line-of-sight (LOS) and 5 for
non-LOS (NLOS) conditions.
Figure 1 shows Model D delay profile with clusters outlined by exponentia